High-performance distributed fiber sensing system based on ehz ultrafast pulse scanning

ABSTRACT

A high-performance distributed fiber sensing system based on EHz ultrafast pulse scanning. During testing of a disturbance signal, an internally frequency converted pulse light emitted by an EHz ultrafast pulse scanning laser enters a sensing fiber after passing through a circulator, and a backward Rayleigh scattering signal transmitted by the sensing fiber enters an unbalanced Michelson interferometer after passing through a coupler. By designing an arm length difference between two interference arms, interferences sequentially occur for the backward Rayleigh scattering light at a position where lengths of two adjacent arms differ. A signal received after passing through the unbalanced Michelson interferometer includes a phase difference signal caused by an external disturbance signal in the sensing fiber. Finally, variations of the phase difference signal over time are demodulated by using a phase demodulation unit, so that a dynamic measurement of the disturbance signal in the sensing fiber may be performed.

CROSS-REFERENCE TO RELATED APPLICATIONS

The present application claims priority under 35 U.S.C 119(a) to Chinese Application No. 201910611274.7, filed on Jul. 8, 2019, which is incorporated herein by reference in its entirety.

TECHNICAL FIELD

This application relates to the field of distributed fiber sensing technologies, and in particular, to a high-performance distributed fiber sensing system based on EHz (exahertz) ultrafast pulse scanning.

BACKGROUND

The distributed fiber sensing technology may continuously sense and measure the physical quantities to be measured, which are distributed along a length direction of a fiber, and can integrate functions of sensing and transmitting. In this way, not only the multidimensional distribution status information for space and time of the distributed environmental parameters on an entire fiber length can be continuously measured, but also the distributed measurement information can be transmitted to an information processing center in a real time manner without losses. Meanwhile, a sensing system based on the distributed fiber sensing technology has advantages of having a simple structure, being easy to use, with low signal obtaining costs in a unit length, being a good cost effective solution, and the like. Therefore, this technology is widely applied to many important military and civilian fields such as border security, pipeline leakage, seismic wave exploration, and hydrophone detection.

The distributed fiber sensing technology may be classified into two technologies of OTDR (optical time domain reflectometry) and OFDR (optical frequency domain reflectometry). Compared with the OTDR, under a condition of a same dynamic range, the OFDR requires much smaller optical power of a light source, where the reduction of the optical power of the light source may avoid influences brought by non-linear scattering of a fiber. Therefore, the OFDR has a higher sensibility. In addition, the OFDR is significantly advantageous in an indicator of an ultra-high spatial resolution, and the spatial resolution thereof depends on a wavelength tuning range of the light source. If the light source has a sufficiently wide tuning range, a very high spatial resolution can be achieved. However, at present, the OFDR technology is mainly used for static measurements; and dynamic measurements for a disturbance signal are still being researched.

SUMMARY

Embodiments of this application provide a high-performance distributed fiber sensing system based on EHz ultrafast pulse scanning, to dynamically measure a disturbance signal in a sensing fiber.

A high-performance distributed fiber sensing system based on EHz ultrafast pulse scanning, wherein the system may comprise an EHz ultrafast pulse scanning laser, a circulator, a sensing fiber, a coupler, a first interference arm, a second interference arm, Faraday rotation mirrors, and a phase demodulator, wherein the EHz ultrafast pulse scanning laser may comprise a pump laser source, a first wavelength division multiplexer, a cascaded phase-shifted fiber grating, a second wavelength division multiplexer, a third wavelength division multiplexer, a plurality of electro-optic modulators, and a controller to which the plurality of electro-optic modulators are connected; an output end of the pump laser source is connected to a first end of the first wavelength division multiplexer; the cascaded phase-shifted fiber grating is composed of a plurality of phase-shift gratings that are engraved on a doped fiber, the phase-shift gratings having different central window wavelengths and a wavelength interval between the adjacent central window wavelengths being a preset fixed value, and the cascaded phase-shifted fiber grating is connected to a second end of the first wavelength division multiplexer; a third end of the first wavelength division multiplexer is connected to an end of the second wavelength division multiplexer; a laser light output from respective wavelength output channel of the second wavelength division multiplexer is transmitted to respective one of the electro-optic modulators; the controller is configured to select sequentially, within a preset duration, respective one electro-optic modulator of the plurality of electro-optic modulators according to a preset time interval; an end of the third wavelength division multiplexer is connected to an output end of each of the electro-optic modulators, and the other end thereof is connected to a first end of the circulator, a second end of the circulator being connected to the sensing fiber, and a third end of the circulator being connected to a first end of the coupler; a second end of the coupler is connected to an end of the first interference arm and an end of the second interference arm, respectively, the other end of the first interference arm and the other end of the second interference arm being connected to respective one of the Faraday rotation mirrors, respectively, and lengths of the first interference arm and the second interference arm are not equal; and the phase demodulator is connected to a third end of the coupler, and is configured to demodulate a phase change caused by a disturbance signal in the sensing fiber.

Optionally, the coupler is a 3×3 coupler, and the phase demodulator comprises a first photoelectric detector, a second photoelectric detector, a third photoelectric detector, and a phase demodulation unit, wherein each of the first photoelectric detector, the second photoelectric detector, and the third photoelectric detector is connected to the 3×3 coupler, and is configured to receive a backward Rayleigh scattering interference light returned from the first interference arm and the second interference arm, and to generate a corresponding electrical signal based on the backward Rayleigh scattering interference light; and the phase demodulation unit is connected to the first photoelectric detector, the second photoelectric detector, and the third photoelectric detector, and is configured to process the electrical signals output by the first photoelectric detector, the second photoelectric detector, and the third photoelectric detector, and demodulate the phase change caused by the disturbance signal in the sensing fiber.

Optionally, a phase modulator is further disposed on the first interference arm, and the phase demodulator comprises a fourth photoelectric detector and a phase demodulation unit, wherein the fourth photoelectric detector is connected to the coupler, and is configured to receive a backward Rayleigh scattering interference light returned from the first interference arm and the second interference arm, and to generate a corresponding electrical signal based on the backward Rayleigh scattering interference light; and the phase demodulation unit is connected to the fourth photoelectric detector, and is configured to process the electrical signal output by the fourth photoelectric detector, and demodulate the phase change caused by the disturbance signal in the sensing fiber.

Optionally, a rotation angle of the Faraday rotation mirror is 90°.

Optionally, the EHz ultrafast pulse scanning laser further comprises an isolator, wherein an end of the isolator is connected to the third end of the first wavelength division multiplexer, and the other end thereof is connected to an end of the second wavelength division multiplexer.

Optionally, the EHz ultrafast pulse scanning laser further comprises a signal amplifier, wherein an end of the signal amplifier is connected to the third end of the first wavelength division multiplexer, and the other end thereof is connected to an end of the second wavelength division multiplexer.

Optionally, the doped fiber is composed of N numbers of sub doped fibers connected in parallel, where N≥2, wherein a plurality of phase-shift gratings are engraved on each of the sub doped fibers, the phase-shift gratings having different center wavelengths and a wavelength difference between the adjacent center wavelengths being a first preset fixed value; and the first preset fixed value is N times of the wavelength interval between the wavelengths output by the doped fiber.

Optionally, the pump laser source comprises a first sub pump laser source and a second sub pump laser source, and the first wavelength division multiplexer comprises a first sub wavelength division multiplexer and a second sub wavelength division multiplexer, wherein an output end of the first sub pump laser source is connected to a first end of the first sub wavelength division multiplexer, and an output end of the second sub pump laser source is connected to a first end of the second sub wavelength division multiplexer; the doped fiber is connected to a second end of the first sub wavelength division multiplexer and a second end of the second sub wavelength division multiplexer, respectively; and a third end of the first sub wavelength division multiplexer or the second sub wavelength division multiplexer is connected to an end of the second wavelength division multiplexer.

It can be seen from the foregoing technical solutions that according to the high-performance distributed fiber sensing system based on EHz ultrafast pulse scanning provided in the embodiments of this application, in this system an unbalanced Michelson interferometer is formed by two interference arms whose arm lengths are unequal and Faraday rotation mirrors connected to the interference arms. During testing of a disturbance signal, an internally frequency converted pulse light emitted by the EHz ultrafast pulse scanning laser enters the sensing fiber after passing through the circulator, and a backward Rayleigh scattering signal transmitted by the sensing fiber enters the unbalanced Michelson interferometer after passing through a coupler. By designing an arm length difference between the two interference arms to be greatly smaller than lengths of the arms, in a pulse scanning cycle, interferences are sequentially occurred for the backward Rayleigh scattering light at a position where lengths of two spatially adjacent interference arm differ. In this way, a signal received after passing through the unbalanced Michelson interferometer includes a phase difference signal caused by an external disturbance signal in the sensing fiber. Finally, variations of the phase difference signal over time are demodulated by using a phase demodulation unit, so that a dynamic measurement of the disturbance signal in the sensing fiber may be performed.

In addition, k numbers of pulse lights whose frequencies linearly increase are included in the internally frequency converted pulse emitted by the EHz ultrafast pulse scanning laser. For a frequency response range, a total interference light intensity is performed with low-pass filtering and then a zero-difference frequency component is taken therefrom, and the entire system can be equivalent to k numbers of OTDR systems that have different frequencies and simultaneously work in a time sequence. After the relative phase results obtained by phase demodulation are arranged in the time sequence as well, the frequency response range of the system is improved by k times as compared with the single-frequency OTDR system. Meanwhile, the internally frequency converted pulse light emitted by the EHz ultrafast pulse scanning laser can form a plurality of sounding laser sequences that have different wavelengths and a relatively short time interval in a time domain within a preset pulse width range in a frequency domain, thus being able to effectively resolve a problem that it is difficult for a distributed sensing system to monitor simultaneously in terms of long distance, high-band signal, and high spatial resolution.

BRIEF DESCRIPTION OF THE DRAWINGS

To more clearly describe the technical solutions of the present application, the accompanying drawings to be used in the embodiments are briefly illustrated below. Obviously, persons of ordinary skills in the art can also derive other accompanying drawings according to these accompanying drawings without a creative effort.

FIG. 1 is a basic schematic structural diagram of a high-performance distributed fiber sensing system based on EHz ultrafast pulse scanning according to an embodiment of this application;

FIG. 2 is a schematic diagram of the spatial differential interference of a backward Rayleigh scattering light that passes through a Michelson interferometer in FIG. 1;

FIG. 3 is a schematic diagram of a timing correspondence between a delay signal and an original signal in FIG. 2;

FIG. 4 is a basic schematic structural diagram of an EHz ultrafast pulse scanning laser according to an embodiment of this application;

FIG. 5 is a basic schematic structural diagram of an EHz ultrafast pulse scanning laser according to another embodiment of this application;

FIG. 6 is a basic schematic structural diagram of a high-performance distributed fiber sensing system based on EHz ultrafast pulse scanning according to another embodiment of this application;

FIG. 7 is a schematic diagram of an optical path of phase demodulation of a 3×3 coupler in FIG. 6;

FIG. 8 is a functional block diagram of a phase demodulation algorithm based on a 3×3 coupler according to an embodiment of this application;

FIG. 9 is a functional block diagram of an orthogonally optimized phase demodulation algorithm of a 3×3 coupler according to an embodiment of this application;

FIG. 10 is a basic schematic structural diagram of a high-performance distributed fiber sensing system based on EHz ultrafast pulse scanning according to still another embodiment of this application; and

FIG. 11 is a functional block diagram of a phase carrier demodulation algorithm according to an embodiment of this application.

DETAILED DESCRIPTION OF THE EMBODIMENTS

Exemplary embodiments are described herein in detail, and examples thereof are shown in the accompanying drawings. When the descriptions below relate to the accompanying drawings, unless otherwise stated, same numerals in different accompanying drawings indicate same or similar elements. Implementations described in the following exemplary embodiments do not represent all implementations consistent with the present invention. On the contrary, these implementations are merely examples of a device and a method that are described in detail in the appended claims and that are consistent with some aspects of the present invention.

At present, static measurements by using the OFDR technology is relatively mature. However, there is no relatively complete system to measure a high-band disturbance signal. Aiming at this problem, a high-performance distributed fiber sensing system based on EHz ultrafast pulse scanning that can demodulate the phase information of the disturbance signal is provided in the embodiments.

FIG. 1 is a basic schematic structural diagram of a high-performance distributed fiber sensing system based on EHz ultrafast pulse scanning according to an embodiment of this application. As shown in FIG. 1, the system includes an EHz ultrafast pulse scanning laser 10, a circulator 20, a sensing fiber 30, a coupler 40, a first interference arm 51, a second interference arm 53, Faraday rotation mirrors 52 and 54, and a phase demodulator 60.

A C1 port of the circulator 20 is connected to an output end of the EHz ultrafast pulse scanning laser 10, a C2 port of the circulator 20 is connected to the sensing fiber 30, and a C3 port of the circulator 20 is connected to a first end of the coupler 40. A second end of the coupler 40 is connected to an end of first interference arm 51 and an end of the second interference arm 53, respectively. The other end of the first interference arm 51 and the other end of the second interference arm 53 are connected to one Faraday rotation mirror, respectively, and lengths of the first interference arm 51 and the second interference arm 53 are not equal. The phase demodulator 60 is connected to a third end of the coupler 40, and is configured to demodulate a phase change caused by a disturbance signal in the sensing fiber 30. In this embodiment, a structure formed by the first interference arm 51, the second interference arm 53, the Faraday rotation mirrors, and the phase demodulator 60 is referred to as an unbalanced Michelson interferometer. In this embodiment, a rotation angle of the Faraday rotation mirror (FRM) is set to 90°, but is not limited this value. In this way, an optical signal can be transmitted, and the polarization influence may be eliminated as well.

In this embodiment, the waveform characteristics of a Rayleigh scattering light that is received at any time by the system, is described based on a one-dimensional pulse response model of backward Rayleigh in a fiber. A fiber having a length of L is divided into N scattering units, where Δl=L/N indicates a length of the scattering unit. Assuming that each scattering unit is completely independent, τ₀=2nfΔl/c is defined as unit scattering time. A light input to the sensing fiber 30 is a high-coherency pulse light that is internally frequency converted, as designed herein, which is formed by splicing consecutively k numbers of ultra short pulse lights whose frequencies fk increase linearly, where an interval between two adjacent frequencies is a fixed value Δf₀. If an optical pulse width for each frequency is ω, a total pulse width is k*w. Therefore, this high-coherency pulse light that is internally frequency converted is incident from a position of l=0 into the sensing fiber 30, and an amplitude of a backward Rayleigh scattering signal obtained at an input end of the sensing fiber 30 may be expressed as:

$\begin{matrix} {{E_{Rs}(t)} = {\sum\limits_{m = 1}^{N}{\sum\limits_{i = 1}^{k}{a_{m}{\exp \left\lbrack {j\; 2\; \pi \; {f_{k}\left( {t - \tau_{m}} \right)}} \right\rbrack}{{rect}\left( \frac{t - \tau_{m}}{\omega} \right)}{{rect}\left( \frac{t - \tau_{m}}{k\; \omega} \right)}}}}} & (1) \end{matrix}$

In formula (1), a_(m) represents an amplitude of the backward Rayleigh scattering at an arbitrary m^(th) scattering point in the fiber; and τ_(m) represents a time delay at the arbitrary m^(th) scattering point in the fiber, and a relationship between τ_(m) and a fiber length l_(m) of the arbitrary m^(th) scattering point in the fiber from the input end is:

$\begin{matrix} {\tau_{m} = {\frac{2\; n_{f}l_{m}}{c} = {{m\; \frac{2\; n_{f}\Delta \; l}{c}} = {m\; \tau_{0}}}}} & (2) \end{matrix}$

In formula (2), c represents a speed of light in vacuum, n_(f) represents a refractive index of the fiber, and a rectangle function

${{rect}\left( \frac{t - \tau_{m}}{\omega} \right)} = 1$

when

${0 \leq {{rect}\left( \frac{t - \tau_{m}}{\omega} \right)} \leq 1},{{{and}\mspace{14mu} {{rect}\left( \frac{t - \tau_{m}}{\omega} \right)}} = 0}$

in other cases.

In this way, the information at a point in the fiber is described by using a backward Rayleigh scattering optical signal at a corresponding time, and variations of the scattering light can reflect the contents included in the information at this point.

Further, the backward Rayleigh scattering light generated in the sensing fiber 30 enters, after passing through the coupler 40, the Michelson interferometer in which a length difference between the interference arms is s. When the length difference s is much smaller than a length L of the interference arm in the interferometer, in a pulse scanning cycle, interferences are sequentially occurred for the backward Rayleigh scattering light at a position where lengths of two spatially adjacent arms in the interferometer differ, this is, referred to as spatial differential interference. FIG. 2 is a schematic diagram of the spatial differential interference of the backward Rayleigh scattering light that passes through the Michelson interferometer in FIG. 1. As shown in FIG. 2, in this embodiment, a signal returned from the second interference arm 53 that is relatively shorter is referred to as an original signal, a signal returned from the first interference arm 51 is referred to as a delay signal, and an optical path difference between the original signal and the delay signal is 2n_(f)s.

Assuming a delay introduced by the interferometer τ_(s)=2n_(f)s/c, an amplitude of the delay signal may be expressed as:

$\begin{matrix} {{E_{d}(t)} = {\sum\limits_{n = 1}^{N}{\sum\limits_{i = 1}^{k}{a_{n}{\exp \left\lbrack {j\; 2\; \pi \; {f_{k}\left( {t - \tau_{n} - \tau_{s}} \right)}} \right\rbrack}{{rect}\left( \frac{t - \tau_{n} - \tau_{s}}{w} \right)}{{rect}\left( \frac{t - \tau_{n} - \tau_{s}}{kw} \right)}}}}} & (3) \end{matrix}$

FIG. 3 is a schematic diagram of a timing correspondence between the delay signal and the original signal in FIG. 2. As shown in FIG. 3, the time sequence of the delay signal is in one-to-one correspondence to that of the original signal, that is, the backward scattering optical signal incident into the interferometer. Assuming that the quantity of scattering unit points in the fiber with a length of s is S_(L), the time sequence of the delay signal satisfies n=m+S_(L).

Therefore, the total interference light intensity received by the interferometer may be expressed as:

$\begin{matrix} \begin{matrix} {{I(t)} = {\left\lbrack {{E_{Rs}(t)} + {E_{d}(t)}} \right\rbrack \cdot \left\lbrack {{E_{Rs}(t)} + {E_{d}(t)}} \right\rbrack^{*}}} \\ {= {\sum\limits_{m = 1}^{N}{\sum\limits_{i = {m + 1}}^{N}{\sum\limits_{p = 1}^{k}{a_{m}a_{i}{\cos \left( {{2\; \pi \; p\; \Delta \; f_{0}w} + \phi_{mi}} \right)}}}}}} \\ {{{{{rect}\left( \frac{t - \tau_{m}}{w} \right)}{{rect}\left( \frac{t - \tau_{m}}{kw} \right)}{{rect}\left( \frac{t - \tau_{i}}{w} \right)}{{rect}\left( \frac{t - \tau_{i}}{kw} \right)}} +}} \\ {{\sum\limits_{n = 1}^{N}{\sum\limits_{j = 1}^{N}{\sum\limits_{p = 1}^{k}{a_{n}a_{j}{\cos \left( {{2\; \pi \; p\; \Delta \; f_{0}w} + \phi_{nj}} \right)}}}}}} \\ {{{{rect}\left( \frac{t - \tau_{n} - \tau_{s}}{w} \right)}{{rect}\left( \frac{t - \tau_{n} - \tau_{s}}{kw} \right)}{{rect}\left( \frac{t - \tau_{j} - \tau_{s}}{w} \right)}{rect}}} \\ {{\left( \frac{t - \tau_{j} - \tau_{s}}{kw} \right) + {2{\sum\limits_{m = 1}^{N}{\sum\limits_{n = 1}^{N}{\sum\limits_{p = 1}^{k}{a_{m}a_{n}{\cos \left( {{2\; \pi \; p\; \Delta \; f_{0}w} + \phi_{mns}} \right)}}}}}}}} \\ {{{{rect}\left( \frac{t - \tau_{m}}{w} \right)}{{rect}\left( \frac{t - \tau_{m}}{kw} \right)}{{rect}\left( \frac{t - \tau_{n} - \tau_{s}}{w} \right)}{{rect}\left( \frac{t - \tau_{n} - \tau_{s}}{kw} \right)}}} \end{matrix} & (4) \end{matrix}$

In formula (4), a multi-level difference-frequency term 2πpΔf₀w is included. Meanwhile, a phase difference φ_(mns)=4πfn_(f)Δ(n−m)/c+4πfn_(f)s/c. To be specific, the phase difference is a power change of a backward scattering light at a point, which is caused by external disturbance. Therefore, the information about the position, the frequency, the intensity, and the like of an acoustic source can be obtained by measuring a variation curve of an interference signal. For example, the phase change caused by the disturbance signal in the sensing fiber 30 is demodulated by using the phase demodulator 60 that is connected to the third end of the coupler 40.

FIG. 4 is a basic schematic structural diagram of an EHz ultrafast pulse scanning laser according to an embodiment of this application. As shown in FIG. 4, the laser mainly includes a pump laser source 101, a first wavelength division multiplexer 102, a cascaded phase-shifted fiber grating 103, a second wavelength division multiplexer 104, and a wavelength selection exporter 105.

In terms of connection, an output end of the pump laser source 101 is connected to a first end of the first wavelength division multiplexer 102, so that most of pump lights can be coupled into the cascaded phase-shifted fiber grating 103 through a second end of the first wavelength division multiplexer 102.

The cascaded phase-shifted fiber grating 103 is composed of a plurality of phase-shift gratings that are engraved on one doped fiber or more doped fibers connected in series, the phase-shift gratings having different central window wavelengths and a wavelength interval between the adjacent central window wavelengths being a preset fixed value. In other words, the cascaded phase-shift fiber grating 103 is composed of a plurality of phase-shift gratings that abut against each other and have a uniform periodic structure. Specifically, the cascaded phase-shifted fiber grating 103 may be prepared by using a phase mask moving method. In addition, the phase-shift gratings can be engraved on a plurality of doped fibers connected in parallel.

Compared with the conventional multi phase-shift gratings, the number of cascades in the cascaded phase-shifted fiber grating 103 designed in this embodiment does not affect a width of a transmitting spectrum. Each of the phase-shift gratings opens a transmitting window at a corresponding wavelength position, and a bandwidth is close to that in a case of single phase shift. Thus, it has advantages of having transmitting wavelengths with good uniformity and having a stable output power, thereby facilitating a stable power of a narrow-linewidth output of a multi-wavelength laser.

Each of the phase-shift gratings in the cascaded phase-shifted fiber grating 103 can ensure, by using an ultra-narrow band transmitting peak thereof, that in a resonated laser cavity only a single longitudinal mode is existed, so as to obtain stable characteristics of a single-mode narrow-linewidth laser light. In this way, the cascaded phase-shifted fiber grating 103 can be excited by the pump laser source 101 to output a plurality of narrow-linewidth laser signals. For example, in this embodiment, twenty phase-shift gratings are engraved on one erbium doped fiber. The wavelength interval between the adjacent central window wavelengths is 0.2 nm, that is, a distance between the respective central window wavelengths λ₁, λ₂, λ₃, λ₄, λ₅, λ₆, . . . , λ₁₉, and λ₂₀ is 0.2 nm. In this way, laser lights that have a fixed wavelength difference of 0.2 nm and a wavelength range of 1548 nm˜1551.8 nm may be formed in a frequency domain. It should be noted that the foregoing wavelength interval of the phase-shift gratings is not limited to 0.2 nm, and may be any other values. However, because each of the phase-shift gratings has a bandwidth in the wavelength, in order to avoid overlapping, the wavelength interval is set to be greater than or equal to 0.2 nm in this embodiment.

Further, the laser lights output by the cascaded phase-shifted fiber grating 103 are output to the second wavelength division multiplexer 104 through a third end of the first wavelength division multiplexer 102. By using the second wavelength division multiplexer 104, light signals with different wavelengths can be transmitted in different optical channels simultaneously, without interfering with each other. In addition, in this embodiment, an isolator 107 is further disposed between the first wavelength division multiplexer 102 and the second wavelength division multiplexer 104. In this way, the laser lights output by the first wavelength division multiplexer 102 can merely be unidirectionally transmitted, in a fiber path, along an output direction of the laser lights, thereby effectively preventing the backward reflection and scattering effects from affecting the output stability of the laser, or preventing the feedback lights from damaging the laser after being input to the doped fiber through the wavelength division multiplexer.

In this embodiment, a signal amplifier 108 is further disposed between the first wavelength division multiplexer 102 and the second wavelength division multiplexer 104, so as to amplify the optical signals. An end of the signal amplifier 108 is connected to an output end of the isolator 107, and the other end is connected to an end of the second wavelength division multiplexer 104. If the isolator 107 is not disposed, an end of the signal amplifier 108 may be connected to the third end of the first wavelength division multiplexer 102. Specifically, depending on the wavelengths of the laser lights output by the cascaded phase-shifted fiber grating 103, the signal amplifier 108 may be an erbium doped fiber amplifier, a ytterbium doped fiber amplifier, or the like.

The wavelength selection exporter 105 in this embodiment includes a plurality of electro-optic modulators (EOM) and a controller to which the plurality of EOMs are connected. The laser light output from respective wavelength output channel of the second wavelength division multiplexer 104 is transmitted to respective one of the EOMs. The controller outputs a control signal to control the EOMs to work, so as to achieve an output with a certain wavelength, that is, within a preset duration, respective one EOM of the plurality of EOMs is sequentially selected according to a preset time interval, so as to form a sequence of wavelengths with a fixed time interval in a time domain. In this way, ultrafast modulation is performed on the foregoing laser lights having the plurality of wavelengths, by using a time-domain control method based on the EOMs. Thus, an internally frequency converted pulse light formed by splicing consecutively a plurality of pulse lights whose frequencies linearly increase is obtained.

For example, when the control signal output by the controller is at a low level, the EOM does not output; and when the control signal is at a high level, the EOM outputs. Assuming that the second wavelength division multiplexer 104 outputs laser lights having twenty wavelengths, and each of the wavelength output channels is correspondingly connected to respective one of the EOMs. The controller controls, in a duration of 0˜5 ns, a corresponding channel ctl1 of a laser light having a first wavelength to be at a high level, and in a duration of 5˜10 ns, controls a second channel ctl2 to be at a high level, and so on. In this way, the laser lights having twenty wavelengths can be arranged in a pulse width of 100 nanoseconds at an equal time interval, so as to form the EHz ultrafast modulation of the laser.

It should be noted that the foregoing wavelength selection exporter 105 is not limited to a modulation manner of the electro-optical modulators and the controller, and may be any other manners, as long as during the preset duration, the laser lights having plurality of wavelengths, which are output by the second wavelength division multiplexer 104, can be selected to be sequentially output according to a preset time interval, so as to form a sequence of wavelengths with a fixed time interval. For example, the modulation manner may alternatively be acousto-optic modulation, but the electro-optic modulation manner has an advantage of having a faster modulation frequency. In addition, the doped fiber in this embodiment is an active fiber obtained by doping various rare earth ions in the fiber base material, and may be an erbium (Er) doped fiber, a ytterbium (Yb) doped fiber, or a thulium (Tm) doped fiber. The pump source is a semiconductor laser, of which a center wavelength of an output laser light matches with an absorption wavelength of the doped fiber. Correspondingly, a center wavelength of the erbium (Er) doped fiber is 980 nm or 1480 nm, a center wavelength of the ytterbium (Yb) doped fiber is 915 nm or 975 nm, and a center wavelength of the thulium (Tm) doped fiber is 793 nm or 1560 nm. Certainly, the pump source may alternatively be other laser or laser diode that can emit the required pump lights.

Further, in this embodiment, in order to enable that the internally frequency converted pulse light output by the wavelength selection exporter 105 can be transmitted in one fiber, a third wavelength division multiplexer 106 is disposed at an output end of the wavelength selection exporter 105. An output end of the third wavelength division multiplexer 106 is configured to be connected to the C1 port of the circulator 20. The wavelength interval of the laser lights output by the cascaded phase-shifted fiber grating 103 is relatively short, and therefore, in this embodiment, the second wavelength division multiplexer 104 and the third wavelength division multiplexer 106 may be a dense wavelength division multiplexer.

In this way, according to formula (4), the total interference light intensity is performed with high-pass filtering and the difference-frequency component is taken therefrom. By using a matching filter technology developed from the microwave radar technology, a pulse compression effect can be achieved by performing a convolution on the relevant received data and a complex conjugate function that is in direct proportion to a signal waveform. Compared with a single-frequency OTDR system, the pulse width is narrowed down to 1/k of the original width, and the spatial resolution of the system finally satisfies that

$D = {\frac{c}{2\; n_{f}\Delta \; f_{0}}.}$

Meanwhile, for a frequency response range, the total interference light intensity is performed with low-pass filtering and the zero-difference frequency component is taken therefrom, and the entire system can be equivalent to k numbers of OTDR systems that have different frequencies and simultaneously work in a time sequence. After the relative phase results obtained by phase demodulation are arranged in the time sequence as well, the frequency response range of the system is improved by k times as compared with the single-frequency OTDR system. Meanwhile, the internally frequency converted pulse light emitted by the EHz ultrafast pulse scanning laser can form a plurality of sounding laser sequences that have different wavelengths and a relatively short time interval in a time domain within a preset pulse width range in a frequency domain, thus being able to effectively resolve a problem that it is difficult for a distributed sensing system to monitor simultaneously in terms of long distance, high-band signal, and high spatial resolution.

FIG. 5 is a basic schematic structural diagram of an EHz ultrafast pulse scanning laser according to another embodiment of this application. As shown in FIG. 5, the EHz ultrafast pulse scanning laser in this embodiment mainly differs from the EHz ultrafast pulse scanning laser provided in FIG. 4 in that, the cascaded phase-shifted fiber grating 103 in this embodiment is composed of a plurality of phase-shift gratings that have different central window wavelengths, which are engraved on two doped fibers connected in parallel. That is, a first cascaded phase-shifted fiber grating 1031 and a second cascaded phase-shifted fiber grating 1032 are included.

For example, ten phase-shift gratings with an wavelength interval of 0.4 nm may be engraved on an erbium doped fiber of the first cascaded phase-shifted fiber grating 1031, and corresponding output wavelengths are λ₁, λ₃, λ₅, . . . , and λ₁₉, and ten phase-shift gratings with an wavelength interval of 0.4 nm may be engraved on an erbium doped fiber of the second cascaded phase-shifted fiber grating 1032, and corresponding output wavelengths are λ₂, λ₄, λ₆, . . . , and λ₂₀. In this way, the wavelength interval of the corresponding phase-shift gratings on the two erbium doped fibers are 0.2 nm, that is, a distance between respective λ₁, λ₂, λ₃, λ₄, λ₅, λ₆, λ₁₉, and λ₂₀ is 0.2 nm. Two erbium doped fibers are connected in parallel to form twenty distributed feedback laser wavelengths. In this way, the overlapping in wavelength may be avoided by means of a parallel connection, thus further reducing the output wavelength interval.

It should be noted that the foregoing cascaded phase-shifted fiber grating 103 is not limited to a manner of connecting two cascaded phase-shifted fiber gratings in parallel, and may be formed by any quantity of cascaded phase-shifted fiber gratings. In addition, the quantity of the phase-shift gratings engraved on the doped fiber of the respective cascaded phase-shifted fiber gratings is not limited to a same value, as long as the wavelength difference between the adjacent central window wavelengths of the phase-shift gratings engraved on the respective doped fibers is a first preset fixed value, and the first preset fixed value is N times of the wavelength interval of the wavelengths output by the cascaded phase-shifted fiber grating 103, where N is the quantity of the cascaded phase-shifted fiber gratings.

Further, in order to enable the pump laser source 101 to provide sufficient pump energy, thus generating a narrow-linewidth laser light with more stable power and a low linewidth drift rate, the pump laser source 101 in this embodiment includes a first sub pump laser source 1011 and a second sub pump laser source 1012. The first wavelength division multiplexer 102 includes a first sub wavelength division multiplexer 1021 and a second sub wavelength division multiplexer 1022. An output end of the first sub pump laser source 1011 is connected to a first end of the first sub wavelength division multiplexer 1021. An output end of the second sub pump laser source 1012 is connected to a first end of the second sub wavelength division multiplexer 1022. The cascaded phase-shifted fiber grating 103 is connected to a second end of the first sub wavelength division multiplexer 1021 and a second end of the second sub wavelength division multiplexer 1022, respectively. A third end of the first sub wavelength division multiplexer 1021 or the second sub wavelength division multiplexer 1022 is connected to an end of the second wavelength division multiplexer 104.

Further, for the demodulation of the phase difference signal, various phase difference demodulation algorithms are provided in this embodiment. FIG. 6 is a basic schematic structural diagram of a high-performance distributed fiber sensing system based on EHz ultrafast pulse scanning according to another embodiment of this application.

As shown in FIG. 6, in this embodiment, a signal output by the EHz ultrafast pulse scanning laser 10 is further chopped (for example, with a pulse width of 100 ns and a scanning frequency of 20 KHz) by using an AOM (acousto-optic modulator 70), so that a laser isolation reaches 60 db. It is amplified by a first erbium doped fiber amplifier (EDFA) 80 and then enters the sensing fiber 30 after passing through the circulator 20, and the backward Rayleigh scattering signal is amplified by a second EDFA 90 and then enters the unbalanced Michelson interferometer to achieve the spatial differential interference. Finally, the phase information is demodulated by using the phase demodulator 60. The phase demodulator 60 includes three photoelectric detectors (PD1, PD2, and PD3), a circulator, and a phase demodulation unit.

FIG. 7 is a schematic diagram of an optical path of phase demodulation of a 3×3 coupler 40 in FIG. 6. As shown in FIG. 7, ports 4 and 6 of the 3×3 coupler 40 are connected with two fibers with different lengths, thus an arm length difference is formed; and Faraday rotation mirrors are connected, and thus two arms of a phase-matching interferometer are formed. By means of adjusting the arm length difference of the phase-matching interferometer, it is possible to form an interference field of the backward Rayleigh scattering light in different adjacent space segments. The backward Rayleigh scattering light is incident to a port 2 of the 3×3 coupler 40 after passing through the circulator 20, and is split into two optical signals by the port 2 of the 3×3 coupler 40. One of the two optical signals enters the port 4 of the 3×3 coupler 40, and is returned to the port 4 of the 3×3 coupler 40 after passing through the first interference arm 51 and the Faraday rotation mirror 52. The other of the two optical signals enters the port 6 of the 3×3 coupler 40, and is returned to the port 6 of the coupler 40 after passing through the second interference arm 53 and the Faraday rotation mirror 54. The two lights are combined and interfered at the 3×3 coupler 40. The interfered backward Rayleigh scattering light enters the PD1 and the PD3 after passing through ports 1 and 3 of the 3×3 coupler 40, and enters the PD2 after passing through the port 2 of the 3×3 coupler 40 and the circulator 20.

The light intensity obtained by the three detectors is expressed as:

I _(p) =D+I ₀ cos[ϕ(t)−(p−1)×(2π/3)], p=1,2,3  (5)

In formula (5), Φ(t)=ϕ(t)+ψ(t); D represents a direct component of the interference signal; I₀ represents an amplitude of an alternating component of the interference signal; p represents a serial number of an optical signal received by the detector, where p=1, 2, 3; ϕ(t) represents a phase difference signal rad caused by the disturbance signal; and ψ(t) represents a phase difference signal rad caused by ambient noises.

Subsequently, the phase demodulation is performed, by using the phase demodulation unit, on the optical signals received by the three detectors. FIG. 8 is a functional block diagram of the phase demodulation algorithm based on the 3×3 coupler according to an embodiment of this application. As shown in FIG. 8, for easy of derivation, it is assumed that A₁˜A₇=1.

Three light intensity signals are added together and multiplied by ⅓, and an output of a first adder is expressed as follows:

$\begin{matrix} {{{- \frac{1}{3}}{\sum\limits_{p = 1}^{3}I_{p}}} = {- D}} & (6) \end{matrix}$

I₁ to I₃ are respectively added with −D to obtain:

a=I ₀ cos[ϕ(t)], b=I ₀ cos[ϕ(t)−2π/3], and c=I ₀ cos[ϕ(t)−4π/3]  (7)

By means of eliminating a direct current term and keeping an alternating current term, differential operations are performed on a, b, and c to obtain:

d=−I ₀φ′(t)sin[φ(t)]

e=−I ₀φ′(t)sin[φ(t)−2π/3]

f=−I ₀φ′(t)sin[φ(t)−4π/3]  (8)

Two differential signals are subtracted and then multiplied by the remaining signal, to obtain:

a(e−f)=√{square root over (3)}I ₀ ²φ′(t)cos²φ(t)

b(f−d)=√{square root over (3)}I ₀ ²φ′(t)cos²[φ(t)−2π/3]

c(d−e)=√{square root over (3)}I ₀ ²φ′(t)cos²[φ(t)−4π/3]  (9)

A sum of a (e−f), b (f−d), and c (d−e) is:

$\begin{matrix} {N = {{{a\left( {e - f} \right)} + {b\left( {f - d} \right)} + {c\left( {d - e} \right)}} = {\frac{3\sqrt{3}}{2}I_{0}^{2}{\phi^{\prime}(t)}}}} & (10) \end{matrix}$

Because I₀ varies due to influence of the system, by eliminating variations of I₀, a quadratic sum of the three signals is:

M=a ² +b ² +c ²=3/2I ₀ ²  (11)

The following may be obtained from dividing formula (10) by formula (11):

P=N/M=√{square root over (3)}φ′(t)  (12)

The following is output after an integral operation:

V _(out)=√{square root over (3)}φ(t)=√{square root over (3)}[ϕ(t)+ψ(t)]  (13)

Because ψ(t) is a slow variable, the phase-change slow variable caused by the environment is eliminated by using a high-pass filter, so as to obtain the disturbance signal, such as the phase change ϕ(t) caused by an acoustic wave signal.

Further, to eliminate the influence of an angle of the 3×3 coupler 40, and convert an operation of the three-path data into two-path data for operation, requirements for on-chip resources are reduced in the phase demodulation algorithm of the 3×3 coupler 40 that is based on a field programmable gate array (FPGA), thereby improving the real time operation. This embodiment further provides an improved phase demodulation algorithm of the 3×3 coupler 40. FIG. 9 is a functional block diagram of an orthogonally optimized phase demodulation algorithm of the 3×3 coupler according to an embodiment of this application. As shown in FIG. 9, in this embodiment, the known angles θ₁ and θ₂ of the 3×3 coupler 40 are substituted into formulas of the three original signals of the 3×3 coupler 40, to obtain:

I ₁ =D+I ₀ cos [ϕ(t)]

I ₂ =D+I ₀ cos [ϕ(t)−θ₁]=D+I ₀[cos ϕ(t)cos θ₁+sin ϕ(t)sin θ₁]

I ₃ =D+I ₀ cos [ϕ(t)−θ₂]=D+I ₀[cos ϕ(t)cos θ₂+sin ϕ(t)sin θ₂]  (14)

A triangular transformation on formula (14) is performed to obtain:

$\begin{matrix} {\begin{bmatrix} I_{1} \\ I_{2} \\ I_{3} \end{bmatrix} = {\begin{bmatrix} 1 & 0 & 1 \\ {\cos \; \theta_{1}} & {\sin \; \theta_{1}} & 1 \\ {\cos \; \theta_{2}} & {\sin \; \theta_{2}} & 1 \end{bmatrix}\begin{bmatrix} {I_{0}\cos \; {\varphi (t)}} \\ {I_{0}\sin \; {\varphi (t)}} \\ D \end{bmatrix}}} & (15) \end{matrix}$

Two orthogonal variables a=I₀ cos ϕ(t) and b=I₀ sin ϕ(t) in formula (15) are solved to obtain:

$\begin{matrix} {\begin{bmatrix} {I_{0}\cos \; {\varphi (t)}} \\ {I_{0}\sin \; {\varphi (t)}} \\ D \end{bmatrix} = {\begin{bmatrix} 1 & 0 & 1 \\ {\cos \; \theta_{1}} & {\sin \; \theta_{1}} & 1 \\ {\cos \; \theta_{2}} & {\sin \; \theta_{2}} & 1 \end{bmatrix}^{- 1}\begin{bmatrix} I_{1} \\ I_{2} \\ I_{3} \end{bmatrix}}} & (16) \end{matrix}$

The following may be obtained through a differential operation:

c=−I ₀φ′(t)sin φ(t)

d=I ₀φ′(t)cos φ(t)  (17)

The following may be obtained by multiplying and then subtracting:

N=ad−bc=I ₀ ²φ′(t)  (18)

The following may be obtained by squaring and then summing the two orthogonal variables:

M=a ² +b ² =I ₀ ²  (19)

The following may be obtained by dividing formula (18) by formula (19):

P=N/M=φ′(t)  (20)

The following may be obtained by performing an integral operation on formula (20):

V _(out)=φ(t)+ψ(t)  (21)

Because ψ(t) is a slow variable, the phase-change slow variable caused by the environment is eliminated by using a high-pass filter, so as to obtain the disturbance signal, such as the phase change ϕ(t) caused by an acoustic wave signal.

FIG. 10 is a basic schematic structural diagram of a high-performance distributed fiber sensing system based on EHz ultrafast pulse scanning according to still another embodiment of this application. As shown in FIG. 10, the high-performance distributed fiber sensing system based on EHz ultrafast pulse scanning in this embodiment mainly differs from that in the foregoing embodiment in that, a phase carrier demodulation manner is used in this embodiment. The phase demodulator 60 includes a photoelectric detector (PD4) and a phase demodulation unit. Meanwhile, a phase modulator 55 is further disposed on the first interference arm 51.

The backward Rayleigh scattering light generated by the sensing fiber 30 is incident to the coupler 40 after passing through the circulator 20, and is split into two optical signals by the first port of the 3×3 coupler 40. One of the two optical signals enters the second port of the coupler 40, and is returned to the coupler 40 after passing through the first interference arm 51 and the Faraday rotation mirror 52. The other of the two optical signals enters the third port of the coupler 40, and is returned to the coupler 40 after passing through the second interference arm 53 and the Faraday rotation mirror 54. The two optical signals are combined and interfered at the coupler 40. The interfered backward Rayleigh scattering light enters the photoelectric detector PD4 after passing through the fourth port of the coupler 40.

According to the coherence principle of light, the light intensity I of the photoelectric detector PD4 may be expressed as:

I=A+B cos Φ(t)  (22)

In formula (22): A represents an average optical power output by the interferometer; B represents an amplitude of an interference signal, where B=κA, and κ≤1 represents visibility of an interference fringe. Φ(t) represents a phase difference of the interferometer. Assuming that Φ(t)=C cos ω₀t+φ(t), formula (22) may be expressed as:

I=A+B cos[C cos ω₀ t+φ(t)]  (23)

In formula (22), C cos ω₀t represents a phase carrier, C represents an amplitude, and ω₀ represents a carrier frequency; φ(t)=D cos ω₀t+Ψ(t), where D cos ω₀t represents a phase change caused by the disturbance signal in the sensing fiber 30, D represents an amplitude, ω_(s) represents a frequency of a sound field signal, Ψ(t) represents a slow variation of an initial phase, which is caused by environmental disturbance or the like. Expanding formula (23) by using a Bessel function to obtain:

$\begin{matrix} {I = {A + {B\left\{ {{\left\lbrack {{J_{0}(C)} + {2{\sum\limits_{k = 0}^{\infty}{\left( {- 1} \right)^{k}{J_{2\; k}(C)}\cos \; 2\; k\; \omega_{0}t}}}} \right\rbrack \cos \; {\varphi (t)}} - {{2\left\lbrack {\sum\limits_{k = 0}^{\infty}{\left( {- 1} \right)^{k}{J_{{2\; k} + 1}(C)}{\cos \left( {{2\; k} + 1} \right)}\omega_{0}t}} \right\rbrack}\sin \; {\varphi (t)}}} \right\}}}} & (24) \end{matrix}$

In formula (24), J_(n)(m) represents an n-order Bessel function value under m-depth of modulation. Assuming k=0 and 1, respectively, a fundamental frequency signal and a frequency doubling signal are obtained.

FIG. 11 is a functional block diagram of a phase carrier demodulation algorithm according to an embodiment of this application. As shown in FIG. 11, the phase demodulator 60, that is, a phase generated carrier (PGC) demodulation device in this embodiment includes multipliers, filters, differentiators, and an integrator. The fundamental frequency signal is multiplied with the detector signal at a first multiplier and then enters a first low-pass filter; the signal is transmitted to a first differentiator and is multiplied with a signal from a second low-pass filter, and then enters an end of a subtractor to be performed with a subtraction operation with a signal from a fourth multiplier. The frequency doubling signal is multiplied with the detector signal at a second multiplier and then enters the second low-pass filter; the signal is transmitted to a second differentiator and is multiplied with a signal from the first low-pass filtering, and then enters an end of the subtractor to be performed with a subtraction operation with a signal from a third multiplier. The two signals are simultaneously transmitted to a subtractor, and after being performed with an operation, it is transmitted to an integrator and a high-pass filter to be demodulated to obtain the sensing signals. To be specific as follows:

The detector signal I that is output by the interferometer and is expanded by using the Bessel function is multiplied with the fundamental frequency signal (with an amplitude of G) and the frequency doubling signal (with an amplitude of H). To overcome the blanking and distortion phenomena of the signal due to fluctuation of an external disturbance signal, the differential-cross multiply (DCM) is performed on the two signals. After being performed with a differential amplification and an integral operation, it is converted as:

B ² GHJ ₁(C)J ₂(C)φ(t)  (25)

The following may be obtained by substituting φ(t)=D cos ω_(s)t+Ψ(t) into formula (25):

B ² GHJ ₁(C)J ₂(C)[D cos ω_(s) t+Ψ(t)]  (26)

It may be learned that a signal after being performed with an integration operation includes D cos ω_(s)t, which is a signal to be tested, and the external environment information. The latter is usually a slow-varying signal, and has a very large amplitude, and thus may be filtered by a high-pass filter. A final output of the system is:

B ² GHJ ₁(C)J ₂(C)D cos ω_(s) t  (27)

The phase-change signal D cos ω_(s)t that is caused by the disturbance signal in the sensing fiber 30 may be solved from formula (27).

Embodiments in this specification are all described in a progressive manner. For same or similar parts between the embodiments, reference may be made to each other. For each embodiment, emphasis is put on differences between this embodiment and other embodiments.

A person skilled in the art would easily conceive of other implementation solutions of the present invention after considering the specification and practicing the invention invented herein. This application is intended to cover any variations, uses, or adaptive changes of the present invention. These variations, uses, or adaptive changes follow the general principle of the present invention and include the common general knowledge or common technical solutions in this technical filed of the present invention. The specification and the embodiments are merely considered as exemplary, and the actual scope and spirit of the present invention are indicated in the following claims. It should be understood that the present invention is not limited to the exact structure that is described above and is shown in the figures, and various modifications and changes can be made thereto, without departing from the scope thereof. The scope of the present invention is merely limited by the appended claims.

As used in this specification and claims, the terms “for example,” “e.g.,” “for instance,” “such as,” and “like,” and the verbs “comprising,” “having,” “including,” and their other verb forms, when used in conjunction with a listing of one or more components or other items, are each to be construed as open-ended, meaning that the listing is not to be considered as excluding other, additional components or items. Other terms are to be construed using their broadest reasonable meaning unless they are used in a context that requires a different interpretation. 

What is claimed is:
 1. A high-performance distributed fiber sensing system based on EHz ultrafast pulse scanning, wherein the system comprises an EHz ultrafast pulse scanning laser, a circulator, a sensing fiber, a coupler, a first interference arm, a second interference arm, Faraday rotation mirrors, and a phase demodulator, wherein the EHz ultrafast pulse scanning laser comprises a pump laser source, a first wavelength division multiplexer, a cascaded phase-shifted fiber grating, a second wavelength division multiplexer, a third wavelength division multiplexer, a plurality of electro-optic modulators, and a controller to which the plurality of electro-optic modulators are connected; an output end of the pump laser source is connected to a first end of the first wavelength division multiplexer; the cascaded phase-shifted fiber grating is composed of a plurality of phase-shift gratings that are engraved on a doped fiber, the phase-shift gratings having different central window wavelengths and a wavelength interval between the adjacent central window wavelengths being a preset fixed value, and the cascaded phase-shifted fiber grating is connected to a second end of the first wavelength division multiplexer; a third end of the first wavelength division multiplexer is connected to an end of the second wavelength division multiplexer; a laser light output from respective wavelength output channel of the second wavelength division multiplexer is transmitted to respective one of the electro-optic modulators; the controller is configured to select sequentially, within a preset duration, respective one electro-optic modulator of the plurality of electro-optic modulators according to a preset time interval; an end of the third wavelength division multiplexer is connected to an output end of each of the electro-optic modulators, and the other end thereof is connected to a first end of the circulator, a second end of the circulator being connected to the sensing fiber, and a third end of the circulator being connected to a first end of the coupler; a second end of the coupler is connected to an end of the first interference arm and an end of the second interference arm, respectively, the other end of the first interference arm and the other end of the second interference arm being connected to respective one of the Faraday rotation mirrors, respectively, and lengths of the first interference arm and the second interference arm are not equal; and the phase demodulator is connected to a third end of the coupler, and is configured to demodulate a phase change caused by a disturbance signal in the sensing fiber.
 2. The distributed fiber sensing system according to claim 1, wherein the coupler is a 3×3 coupler, and the phase demodulator comprises a first photoelectric detector, a second photoelectric detector, a third photoelectric detector, and a phase demodulation unit, wherein each of the first photoelectric detector, the second photoelectric detector, and the third photoelectric detector is connected to the 3×3 coupler, and is configured to receive a backward Rayleigh scattering interference light returned from the first interference arm and the second interference arm, and to generate a corresponding electrical signal based on the backward Rayleigh scattering interference light; and the phase demodulation unit is connected to the first photoelectric detector, the second photoelectric detector, and the third photoelectric detector, and is configured to process the electrical signals output by the first photoelectric detector, the second photoelectric detector, and the third photoelectric detector, and demodulate the phase change caused by the disturbance signal in the sensing fiber.
 3. The distributed fiber sensing system according to claim 1, wherein a phase modulator is further disposed on the first interference arm, and the phase demodulator comprises a fourth photoelectric detector and a phase demodulation unit, wherein the fourth photoelectric detector is connected to the coupler, and is configured to receive a backward Rayleigh scattering interference light returned from the first interference arm and the second interference arm, and to generate a corresponding electrical signal based on the backward Rayleigh scattering interference light; and the phase demodulation unit is connected to the fourth photoelectric detector, and is configured to process the electrical signal output by the fourth photoelectric detector, and demodulate the phase change caused by the disturbance signal in the sensing fiber.
 4. The distributed fiber sensing system according to claim 1, wherein a rotation angle of the Faraday rotation mirror is 90°.
 5. The distributed fiber sensing system according to claim 1, wherein the EHz ultrafast pulse scanning laser further comprises an isolator, wherein an end of the isolator is connected to the third end of the first wavelength division multiplexer, and the other end thereof is connected to an end of the second wavelength division multiplexer.
 6. The distributed fiber sensing system according to claim 1, wherein the EHz ultrafast pulse scanning laser further comprises a signal amplifier, wherein an end of the signal amplifier is connected to the third end of the first wavelength division multiplexer, and the other end thereof is connected to an end of the second wavelength division multiplexer.
 7. The distributed fiber sensing system according to claim 1, wherein the doped fiber is composed of N numbers of sub doped fibers connected in parallel, where N≥2, wherein a plurality of phase-shift gratings are engraved on each of the sub doped fibers, the phase-shift gratings having different center wavelengths and a wavelength difference between the adjacent center wavelengths being a first preset fixed value; and the first preset fixed value is N times of the wavelength interval between the wavelengths output by the doped fiber.
 8. The distributed fiber sensing system according to claim 1, wherein the pump laser source comprises a first sub pump laser source and a second sub pump laser source, and the first wavelength division multiplexer comprises a first sub wavelength division multiplexer and a second sub wavelength division multiplexer, wherein an output end of the first sub pump laser source is connected to a first end of the first sub wavelength division multiplexer, and an output end of the second sub pump laser source is connected to a first end of the second sub wavelength division multiplexer; the doped fiber is connected to a second end of the first sub wavelength division multiplexer and a second end of the second sub wavelength division multiplexer, respectively; and a third end of the first sub wavelength division multiplexer or the second sub wavelength division multiplexer is connected to an end of the second wavelength division multiplexer. 